Electronic converter control circuit



May 25, 1948.

J. L. BOYER 2,442,263

ELECTRONIC CONVERTER CONTROL CIRCUIT Filed April s, 1947 2 Shee'ts-Sheet 1 en l 9.4 as

WITNESSES: INVENTOR W John L. Boyer.

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ATTORNEY May 25, 1948. J. L. BOYER ELECTRONIC CONVERTER CONTROL CIRCUIT Filed April 5, 1947 2 Sheets-Sheet 2 a u a I 14 I6 I5 I u is "1& "A 3A:

INVENTOR John 1.. Bo er.

ATTORN EY WITNESSES: 6am; M

I Patented May 25, 1948 ELECTRONIC CONVERTER CONTROL CIRCUIT John L. Boyer, Wilkinsburg, Pa., assignor to Westinghouse Electric Corporation, East Pittsburgh, Pa., a corporation of Pennsylvania Application April 5, 1947, Serial No. 739,725

8 Claims. (Cl. 172-281) My invention relates to rectifier and inverter converters consisting of a plurality of groups of specially controlled tubes, and tube-circuits therefor. While certain features of our invention are of more general application, my invention was designed particularly for an electronic frequency-changer known as a cycloconverter, and it was still more particularly designed for supplying power from a higher-frequency inputcircuit, generally of a constant frequency, and generally polyphase, to a lower-frequency loadcircuit which may be either single-phase or polyphase, and which may or may not have a variable frequency. The direction of the power-flow may also be reversed. A cycloconverter comprises two groups of tubes for each phase of the outputfrequency, and both groups of tubes are so controlled that they are capable of acting alternately as rectifiers and inverters, thus going through cycles of rectification and inversion, hence the name cycloconverter."

The tubes are preferably either hot-cathode gas-filled tubes, or ignitrons, or other tubes having a control-circuit, and having a main anodeand-cathode circuit which has a tendency to become conducting whenever the tube is fired by having its control-circuit become sufllciently positive to attain at least a critical tube-firing control-voltage with respect to its cathode at a time when its anode is suillciently positive with respect to its cathode; the tube, when fired, having a tendency to remain conducting, independent of the control-element, until the anode becomes less positive than the cathode. The control-element may be a control-grid; or, in the case of an ignitron, the control-element may be either a control-grid or an ignitor.

Numerous arrangements of circuits and electron tubes have been proposed heretofore, for transmitting polyphase energy between two systems of diilerent frequencies. An important application of this type of frequency-changer is the driving of a three-phase sychronous motor, or a three-phase asynchronous motor, for that matter, at different speeds, by changing the frequency. Some of the previously known circuits have the disadvantage that the three outputphases of the electronic converter are not independent of each other. Other disadvantages encountered in previously known circuits of this general type have been the requirement for a reactance-device having a single magnetic circuit for each of the three phases, or a three-phase magnetic circuit, or a converter-circuit having considerable complexity or complication of circuit-diagrams, and poor voltage-regulation of the output-voltages under variable-load conditions.

The principal object of my present invention is to provide a novel type of cycloconverter circuitconnection for the main anode-cathode circuits or the cycloconverter-tubes, whereby most of the foregoing and other disadvantages are eliminated.

A more specifically stated object of my invention is to provide a main anode-cathode circuit for a polyphase-to-polyphase electronic converter of the cycloconverter type, in which a single uncoupled mid-tapped reactor, provided with a single core of its own, is utilized for each outputphase, the output-circuit conductors being connected directly to the midtaps of the several midtapped reactors.

With the foregoing and other objects in view, my invention consists in the circuits, systems, combinations, apparatus, parts and methods hereinafter described and claimed, and illustrated in the accompanying drawing, wherein Figure 1 is a simplified diagrammatic view of circuits and apparatus illustrative of a threephase cycloconverter for supplying a three-phase output-circuit.

Fig. 2 is a simplified view, of similar nature, except that only the main anode-cathode circuits of the cycloconverter-tubes are shown, omitting the control-circuits, and illustrating the embodiment of my invention in a form of embodiment utilizing a three-phase input-circuit and only two cycloconverter-tubes for each half-phase of the output-circuit, and

Figs. 3 to 8 are curve-diagrams which will be referred to in the explanation of the invention.

In Fig. 1, I show a 3-phase input-circuit l, which is energized from a generator 2. An eighteen-tube cycloconverter 3 is utilized to couple the input-circuit I to a 3-phase output-circuit 4A, 4B and 40, preferably having a frequency lower than the input-circuit,

The supply-circuit I may be a constant-frequency (SO-cycle system, or any other alternating current supply-system, usually polyphase, while the output-circuit 4A, 4B, 40 may either be of a constant frequency, such as a 25-cycle system, Or it may be of a variable frequency, which may be controlled.

While I refer to the supply and load circuits I and 4A, etc., as input and output circuits, respectively, I wish it to be understood that the direction of power-flow is reversible, so that power may be interchanged in either direction between these two circuits, the words input and output being utilized merely as a matter of convenience, to refer to circuits which ordinarily serve as the input and output circuits, respectively, in most applications of my invention.

Each of the main power-tubes 3 may be either a hot-cathode gas-filled tube or an ignitron, having a suitable control-electrode. In the drawing, a tiny circle or dot has been placed within the diagrammatic representation 01 each 01' these tubes, as a convention for indicating the presence of gas or vapor, or other means for causing the control-electrode of the tube to become ineffective, in general, to stop the firing of the tube, once the firing has been initiated.

The main anode-cathode circuits of the cycloconverter-tubes may be arranged or connected in any of the ways known for rectiflers and inverters, either single-phase or polyphase, and for any desired number of phases. In the form of embodiment of my invention which is shown in Fig. 1, the cycloconverter-tubes 3 are arranged in six groups numbered Al, A3, A5; A4, A6, A2; BI, B3, B5; B4, B6, B2; Cl, C3, C5; and C4, C6, C2. The letters A, B and C of this nomenclature correspond to the three phases oi the output-circuits 4A, 4B and 4C. The numbers correspond to the phase-numbers 01' a G-phase system of vectors of the input-frequency.

The positive groups or cycloconverter-tubes 3 are those bearing odd numbers, such as the tubes Al, A3 and A5, for example, which supply the positive half-waves of the phase-A output-current for the output-conductor 4A. These tubes are called the positive tubes because their anodes 6 are connected to the respective phase-conductors of the three-phase input-circuit l. The mercury cathodes I oi these positive tubes are connected to a common cathode-circuit 8A. The

corresponding cathode-circuits for the other output-phases are designated 83 and 8C, respectively.

The so-called negative tubes 3 of the cycloconverter are designated by even numbers, such as the tubes Al, A6 and A2, which supply the negative halves of the output-currents in their respective output-phases, such as the output-phase 4A. The cathodes 1 of each of these negative tubes are connected to the respective phase-conductors or the 3-phase input-circuit I, while the anodes 8 of said negative tubes are connected to common anode-conductors 9A, 9B and 90, respectively, for the three output-phases 4A, 4B and 40.

As will be explained later on, each group of tubes, either positive or negative, is capable of supplying substantially the entire voltage-wave 01' the output-phase to which it is connected. When the output-current is at unity displacement-factor, the positive half-waves of current are drawn from the positive tubes, through rectifier action, and the negative half-waves of the current are drawn from the negative tubes, also through rectifier action. However, an important characteristic feature of my cycloconverter is that the output-current does not need to be at unity displacement-factor, and when this is the case, the output-current is not in phase with the output-voltage, so that the part of the current which is out of phase with the voltage is supplied partly by rectifier action, and partly by inverter action.

This circumstance will be explained more in detall, with reference to wave-form diagrams, in the subsequent explanation of the mode of operation or the invention. It is mentioned, here, to

4 emphasize the fact that when I refer to positive tubes and negative tubes, I use the terms "positive" and negative only as a convenience. to refer to currents which are considered to be positive or negative at any particular moment. It should be borne in mind, however, that each cycloconverter-tube 3 is capable of supplying both the positive and negative halves of the outputvoltage wave, by reason of the control-circuit voltage which is supplied to each tube, as each cycloconverter-tube 3 is capable of operating either as a rectifier or as an inverter.

The 3-phase output-circuit 4A, 4B, 40 of Fig. 1 is illustrated as being utilized to energize a variable-speed 3-phase motor III, which may be either an induction motor or a synchronous motor. It is illustrated as having a 3-phase primary winding I I, which is the stator winding of the machine, and it has a rotor I2 which is provided with .a squirrel-cage secondary or damper winding [3,

and it may or may not have a direct-current exciting-winding ll, which may be suitably controlled by automatic or manual means (not shown), as is well understood in the art of synchronous-motor operation.

Fig. 1 shows a novel method and means, according to my present invention, for transferring power from the positive and negative groups of cycloconverter-tubes to the several output-phases 4A, 4B and 4C. The means for transferring power from the cycloconverter-groups to the load-circuit 4A, 4B, and 4C is the same for each phase, so that a description or the means for one phase will sufllce for all three. As shown in Fig. 1, this power-transfer means, for phase A, is in the form of a, paralleling reactor ISA, which has a midtap which is connected to the corresponding outputphase 4A. The terminals of the paralleling reactor ISA are connected respectively to the cathode-bus 8A of the corresponding positive group of tubes, and the anode-bus 9A of the corresponding negative group of tubes. The paralleling reactors for the other two output-phases are designated I513 and I50 respectively.

In Fig. 1, the control-electrodes of the cycloconverter-tubes 3 are illustrated as being the ignitors 20 of the several tubes. The exciting currents for the several ignitors, as illustrated, are supplied, by a known form of exciter-circuit. indicated generally by the numeral 2|, i'rom eighteen gas-filled auxiliary or exciter-tubes 22, only seven 01' which are shown in Fig. 1, the rest having been omitted in order to avoid unnecessary complication of the diagram. Thus, I have illustrated the six auxiliary tubes 22 for exciting the ignitors of the six phase-A cycloconverter-tubes Al, A3, A5: Al, Al, A2, referring to the output-phase A of the outputcircuit conductor 4A. The cycloconverter-tubes of the remaining two phases are similarly controlled, the nature of the control being indicated only for the first tube, BI, 01' the second outputphase, to show the nature of the connections.

The ignitor-energizing tubes 22 have controlgrids 23 which are controlled in a novel manner which constitutes the subject-matter of a copending joint application of C. G. Hagensick and myself, Serial No. 739,724, filed April 5, 1947. The cathodes 24 of all eighteen exciter-tubes 22 are connected to a common cathode-circuit or bus 25, to which is connected a grid-control circuit 26 which includes a negative-bias battery 21, and a conductor 28 which then branches into six branch control-circuits 29A, 29A, 29B, 29B, 29C and 290'. One of these branch control-circuits is utilized for the grids 23 or the ignltor-energiz ing tubes 22 for the three cycloconverter-tubes 3 of eachcf the six groups of cycloconvertertubes. The control-circuit branches for the posi tive cycloconverter-groups are not primed, and control-circuit branches for the negative cycloconverter-groups are primed.

Each of the control-circuit branches 29A, etc., includes a source of a square-topped modulatorwave voltage, phased according to the desired output-phases 4A, 4B and 40, to supply both the positive and negative halves of the outputphases. pending joint application of C. G. Hagensick and myself, I utilize a control-circuit including a common cathode-circuit 25-46, so that the modulator-wave circuit, for each cycloconverter-group (such as the tubes Al, A3, A5), may be a singlepole rotating-commutator bias-controlling means.

This single-pole rotating-commutator biascontrolling means may take various forms, as more particularly set forth in the joint application just mentioned. In Fig. 1, of the accompanying drawing, it comprises a rotating commutator 30, mounted on a shaft 3| which is driven at the synchronous speed corresponding to the desired output-frequency of the output-circuit 4A, 4B, 40, as by means of a motor M. The commutator 36 has one conducting commutatorsegment 32, or one segment for each 360 electrical degrees; and this segment, as set forth in said joint application, has a circumferential extent which is materially less than 180 electrical degrees, as will be subsequently explained in detail. Bearing on the commutator 30 are six commutator-brushes 33 which are spaced by the number of electrical degrees corresponding to twice the number of phases of the output-circuit 4A, 4B, 4C, twice because both positive and negative wave-halves are supplied In Fig. 1, since the output-circuit is three-phase, there are six commutator-brushes 33, spaced 60 electrical degrees apart.

The six commutator-brushes 33 are serially connected, through resistors 34A, 34A, 34B, 34B, 34C and 340, respectively, to the negative terminal 28 of the negative-bias battery 21. The resistors 34A, etc., have intermediate potentiometer-taps 35, which are connected to the respective branch-circuits 29A, etc. The commutator-segment 32, is connected, through a slipring 36, to the positive terminal 26 of the negative-bias battery 21, so that the six potentiometers 34A, etc., serve to periodically reduce the negative bias which is effective in the respective branch-circuits 29A, etc., at the times when the respective potentiometers are energized bytheir respective commutator-brushes 33.

Continuing the description of the grid-control branch-circuits 29A, 29A, 29B, 29B, 29C and 290', as shown in Fig. 1, it will be noted that the two branch-circuits 29A and 29A, for controlling the positive and negative tubes of the output-phase A, are connected to the midpoints of two groups of 3-phase-star-connected secondary windings 31A and 31A, which are energized from a group of 3-phase-connected primary windings 33A of three single-phase peaking-transformers, for supplying the grid-controlling voltage-peaks for controlling the rectifier-operation of the corresponding cycloconverter-tubes 3. The corresponding phases of the rectifier-peaker windings 31A and 31A are connected to the proper phases of a group of open-star G-phase-connected secondary windings 39A which are excited by a group of 3-phase-connected primary windings As more particularly claimed in the co-' 46A oi! three single-phase peaking-transformers for supplying the grid-controlling voltage-peaks for the inverter-operation 01' the respective cycloconverter-tubes 3.

The corresponding peaking-transformers for the output-phase B are indicated at 383 and 403. The corresponding peaking-transformers for the third phase C are indicated at 33C and 46C.

The three groups of rectifier peaking-transformers 38A, 38B and 380 are illustrated as bei excited from a. 3-phase input-frequency circuit 4|, the phase of which is controlled by means of a phase-shifter 42 which is excited from an auxiliary input-frequency circuit 43, energized, through an auxiliary power-transformer 44, from the 3-phase input-circuit l of the cycloconverter. The three groups of inverter peaking-transformers 46A, etc., are excited from a 3-phase input-frequency circuit 45, which is energized, by a phase-shifter 46, from the auxiliary input-frequency circuit 43.

Each of the six sets of peaking-transformer secondaries, such as 31A and 39A, subdivides its branch control-circuits, such as 29A, into as many separate circuits as the number 01' main tubes 3 in each cycloconverter-group, such as Al, A3 and A5. Each cycloconverter-tube 3 thus receives its proper phase-control, through its assigned firing-controlling tube 22.

Tracing the grid-control circuit for controlling the first cycloconverter-tube Al, for example, and starting with the branch-circuit conductor 29A, it will be notedithat the rectifier-peaker winding 41, having a phase corresponding to the voltagephase which is supplied to the main tube Al, is connected in series with the inverter-peaker phase 43, which preferably lags behind the winding 41, although the relative phases may be controlled, to a nicety, by the respective phaseshifters 42 and 46. The output-terminal of the inverter-peaker phase 48 is connected to the gridcircuit 48 of the auxiliary tube 22 which excites the ignitor 20 of the cycloconverter-tube Al.

The ignitor-circuits of the cycloconvertertubes 3 in Fig. 3 are energized from the anodecircuits 5| of the respective auxiliary tubes 22. These anode-circuits are energized from a set of 6-phase star-connected secondary windings 52A, 523, etc.. of exciter-transformers which are illustrated as having B-phase primary windings 53, energized from the auxiliary input-frequency bus 43.

The anode-circuit 5| of each of the auxiliary tubes 22 includes a, rectifier 54 for delivering only the positive half-waves of the energizing-transformer phase, a current-limiting resistor 55, and the primary winding of an insulating transformer 56, the secondary winding of which excites the ignitor-circuit 51, through a rectifier 56 which supplies only the positive peaks to the ignitor. A return-path for the flux-decay current of the insulating transformer 56 is provided, in a known manner, by means of a rectifier 59 which is connected across the transformer-secondary.

The energy-source for each of the anode-cir cuits 5| of the auxiliary or exciting tubes 22 also includes an energy-storing capacitor 60 which is connected in shunt across the anode-circuit, at a point between the resistor 55 and the insulating transformer 56. The capacitor 60 assists in delivering a stron peak-current to the ignitorcircuit when the auxiliary tube 22 becomes conducting. The current-limiting resistor 55 controls the rate at which the capacitor 60 is charged, during the positive half-cycles of the anode-volt.-

7 age which is applied to the tube 22, and the resistor 55 also serves to limit the amount 01' current which is drawn from the transformer-windings 52A, etc., when the auxiliary tube 22 becomes conducting.

The operation of the invention will best be understood with reference to the curve-diagrams of Figs. 3 to 8, which may be considered, for example, with reference to the form of embodiment of the invention which is shown in Fig. 1.

Fig. 3 shows the control-circuit voltages which are applied to the grid-circuit 49 of the ignitorfiring tube 22 for controlling only one of the main cycloconverter-tubes 8, such as the tube AI in Fig. 1, while Fig. shows the grid-control voltages for all of the tubes of the positive-voltage group of tubes Al, A8 and A5, and Fig. 7 shows the gridcontrol voltages for the negative-voltage tubes A4, A6 and A2.

Figs. 4 and 6 show the three sinusoidal voltages, EIE4, Eli-E6, and E5E2, which are supplied to the main anode-cathode circuits of the cycloconverter-tubes 3 from the input-circuit I of Fig. 1; the zero-voltage line I! of Figs. 4 and 6 being the neutral-voltage, such as the generator neutral-voltage 80.

The positive halves of the voltage-waves have the odd numbers as EI E3, E5; while the negative halves have the even numbers, as E4, E6, E2.

In Fig. 4, the heavy-line curve 8 shows substantially the voltage of the cathode-bus, such as the cathode-bus 8A, of one of the -so-called positive groups of cycloconverter-tubes, such as the tubes Al, A8, A5 of Fig. 1, this voltage being plotted with respect to the neutral-point 80.

In Fig. 6, the heavy-line curve 8 shows substantially the voltage of the anode-bus, such as 9A, of one of the so-called negative groups of cycloconverter-tubes, such as the tubes A4. A5, A2 of Fig. 1, this voltage being again plotted with respect to the neutral-point 80.

The voltage of the corresponding output-circuit conductor 4A of Figs. 1, 2 or 3, or the midpoint of the paralleling reactor I5A, is substantially the average of the voltages represented by the heavy-line curves 8 and 9 of Figs. 4 and 6; the output-frequency voltage-drops in the two halves of the paralleling reactor ISA being relatively small, except during the moments when the output-voltages 8 and 9 01' the positive and negative groups of tubes are not equal, resulting in the flow of circulating currents in the paralleling reactor. This output-voltage is shown at 4 in Fig. 8.

In Fig. 5 are shown all of the resultant voltages which are supplied to the three control-circuits of the auxiliary tubes controlling the three positive-voltage tubes Al, A3 and A5 in Fig. 1. The zero-potential line 8 in Fig. 5 represents the potential oi the common control-circuit cathodebus 25 of Fig. 1. The voltage of the controlcircuit conductor 29A of Fig. 1, with respect to the common control-circuit cathode-bus 25, is represented by the square-topped wave-form marked 29 in Fig. 5. The positive peaks of the three rectifier firing transformer secondaries 81A are indicated at RI, R3 and R5 in Fig. 5, and the positive peaks of the three corresponding serially connected phases of the inverter-firing secondary-windings 38A are indicated at II, I3 and I5 in Fig. 5.

The negative peaks of the control-voltages which are applied to the respective firing-controlling tubes 22 of Fig. 1 have been omitted, in

Fig. 5, because they are immaterial, as the gridcircuits are eflective to fire the several tiring controlling-tubes 22 only when the respective grids reach a voltage which is more positive than a certain critical grid-potential, such as is repre-- sented by the dotted horizontal line 84 In Fig. 5.

It will be understood that the control-circuit of each of the grid-firing tubes, such as the top tube 22 which is associated with the cycloconverter-tube AI, receives only the correspondingly numbered peaks RI and II of its own circuit.

Fig. 7 shows the corresponding output-irequency-modulated grid-bias 29' of the controlcircuit conductor 29A of Fig. 1, and also the rectifier-firing and inverter-firing peaks R4, R8, R2, and I4, 16, I2, which are applied to the gridcircuits of the respective firing-controlling tubes 22 which are associated with the cycloconvertertubes A4, A8 and A2 01. Fig. 1.

It will be noted, from Figs. 5 and 7, that the rectifier-firing peaks RI, etc., are smaller than the inverter-firing peaks II, etc., and that the square-topped output-frequency-modulated wave 28 or 29' alternates, at the modulator-frequency, between time-periods of unequal length, in which the modulated grid-bias voltage is alternately high and low. The periods 85 and 85', during which the modulator-frequency grid-bias voltage has the more negative value, are longer than the periods 86 and 88' during which the modulatorfrequency grid-bias voltage has the more positive (or less negative) value.

It will be further noted that the more negative periods 85 and 85' of the modulated grid-bias have such a tube-controlling voltage as to prevent the rectiiying-controlling peaks RI, R2, etc., from making the total grid-voltage sufllciently positive to reach the critical grid-voltage 84 which is necessary to initiate the firing oi the corresponding auxiliary tube 22, and through it, to initiate the firing oi. the associated cycloconverter tube Al, A2, etc.; but this more negative modulated grid-bias 85 or 85 is not suiilcient- 1y negative to block the inverting-controlling operation of the cycloconverter-tubes, because the inverting peaks II, 12, etc., are sufllciently strong to extend up above (or more positive than) the critical grid-voltage 84.

On the other hand, the less negative (or more positive) modulated grid-bias voltage 86 or 8B is sufliciently positive so that it does not block either the rectifier-controlling peaks RI, R2, etc., or the inverter-controlling peaks II, I2, etc., thus permitting both sets of peaks to fire their respective tubes, if the tube-anodes are sumciently positive with respect to the tube-cathodes, at the moment.

As set forth in the aforementioned joint application, the length or time-duration oi the rectification-permitting periods 86 or 86' of Figs. 5 and 7 should be substantially less than electrical degrees of the output-frequency. It is also essential that the time-period between the end, 81, 01' a rectification-permitting period 86' (Fig. '7) of one group, say A4, A6, A2, of a pair oi. groups of cycloconverter-tubes, and the beginning. 88, of the next rectification-permitting period 88 (Fig. 5) of the other group, such as Al, A8, A5, shall be sufllciently long, when measured in terms of the input-frequency, to provide satisfactory operation, as will now be explained.

It the ratio between the output-frequency and the input-frequency is variable, this time-period 81-88, when measured in output-frequency degrees, should be adequate under the extreme conditions of the highest ratio of output-frequency to input-frequency.

In a converter-circuit having a three-phase input to the main tubes; as shown in Fig. 1, it is necessary to have a period 81-88 of at least 60 input-frequency degrees in which the outputfrequency modulator does not permit rectification in either group, and it is usually desirable to provide a somewhat larger time-interval, in order to provide a suitable margin to allow for inaccuracies in the control-circuits. If the main circuits of the converter-tubes were energized for six-phase operation, a time-period 81-88 of at least 120 input-frequency degrees would be required.

The reason for these various requirements will best be understood by a detailed consideration of the operation of the converter, with reference to the curves shown in Figs. 4 to 8.

To determine the operation of the cycloconverter-tubes, it is necessary to know the amount and the polarity of the instantaneous value of the output-current at any moment. In Fig. 8, a lagging output-current is assumed, by way of illustration, as shown by the curve 90. This output-current 90 lags the output-voltage 4 approximately by the output-frequency phase-angle represented by the distance between the voltagezero 9| and the current-zero 92, or the outputfrequency angle between the voltage-zero 93 and the current-zero 94.

, At the first moment shown in Figs. 4 to 8, it is assumed, for example, that the converter-tube A2 is carrying current as a rectifier, as shown by the beginning, 95. of the negative-group voltage-curve 9 in Fig. 6. It must be remembered that the voltage-curve 9 in Fig. 6 represents the anode-voltage of the tube which is carrying current at the moment. The current, at this moment, is negative, as shown by the beginning, 96, of the current-curve 90 in Fig. 8, thus indicating that the current is flowing from the output-circuit 4A to the input-circuit I, at the moment. While the negative-voltage tube A2 is carrying current as a rectifier, its anode-voltage 95 (Fig. 6) is substantially the same as the voltage E2 which is impressed upon its cathode, because the voltage-drop within the tube is small, as compared to the operating-voltage of the tube.

The negative-voltage tube A2 continues to carry the current 96, through rectifier-action, until the next tube A4 of the negative group A4, A6, A2 is fired, which happens when the rectifier-peak R4, in Fig. '1 attains the critical gridvoltage 84, as indicated by the point 91. This point occurs after the crossing-point 98 of the voltage-waves E2 and E4. At the point 91, the instantaneous voltage of the common anodecircuit 9A of the newly firing tube A4 is the same as the anode-voltage of the previously rectifying tube A2, as shown at 99 in Fig. 6. At the same time, the cathode-voltage of the tube A4, which is just being fired, is the instantaneous value of the impressed voltage-wave E4, as indicated at I in Fig. 6. This analysis thus shows that the tube A4, which is just being fired, has its anode-voltage 99 more positive than its cathode-voltage I00, at the instant 81 when the starting-impulse is applied to its control-electrode. This satisfies the conditions necessary for .firing the tube A4.

' A certain commutating time thereupon ensues, as represented by the horizontal distance between the vertical lines 91 and MI, in Fig. 6. During this commutating time, the current is commuted, or changed, from the tube A2 to the tube A4. The length of this commutatlng time depends upon the amount of current which has to be commutated at that particular moment, the reactance of the supply-generator 2, and the voltage-difference 99-100 between the circuits being commutated. The voltage of the anodecircuit 9A of Fig. 1 thereupon changes substantially to the voltage E4 which is supplied to the tube A4, as indicated by the portion, I02, of the heavy curve 0 in Fig. 6.

Soon after the rectifying-firing peak R4 of the tube A4 occurs, as shown in Fig. '1, the inverting-firing peak 12 of the tube A2 occurs, but the tube A2 does not fire at this point, because its cathode-voltage E2, as shown in Fig. 6, is more positive than its anode-voltage which is shown by the portion I02, of the heavy-line curve in Fig. 6.

Thereafter, the rectifying action is changed over to the next tube A6 of the negative group, at the point I03, and the output-voltage becomes substantially the voltage of the impressed voltage-wave E6, as shown at ['04.

Before the time comes for the rectifier-peak R2 of the next negative-voltage tube A5, the modulated grid-bias 29', in Fig. '1, changes from its rectification-permitting value 86, to its blocking value at the moment indicated at 81 in Fig. '1. This moment 81 thus marks the moment after which none of the negative-group tubes A4, A6, or A2 will receive an effective rectificationstarting firing-impulse R4, R6 or R2, of sufllcient strength to reach the critical firing-voltage 84; and this rectification-blocking condition endures as long as the modulated-bias curve 29' has its maximum negative value as shown at 85' in Fig. 7. This blocking-period endures from the point 81 to the point I08 in Fig. '1. As set forth in the copending joint application, this rectification-blocking period should be considerably longer than 180 output-frequency degrees. In Fig. '1, the blocking-period is shown, by way of illustration, as enduring for approximately 210 output-frequency degrees. This means that the duration of the rectification-permitting periods 86 and 86', in Figs. 5 and '1, is approximately I50 output-frequency degrees, in the particular case which I have chosen for illustration in the drawing.

Since there is no immediately following rectitying-impulse to change the current from the rectifying tube A6 to either of the other tubes A2 or A4 of the negative group, after the tube A6 begins rectifying, as indicated by the portion, I04, of the voltage-line in Fig. 6, and since a negative current continues to be drawn by the load, as indicated by the portion, I01, of the load-current curve 90 in Fig. 8, the negative-voltage tube A6 continues to carry current, as a rectifier, until the voltage-zero point Si is reached, in Fig. 6, after which the tube still continues to carry current, through inverter-action, during a portion of the positive half of the voltage-wave, which is shown at E3 in Fig. 6. This action continues until the inverter-firing peak I2 attains a sufliciently positive value, as indicated by the point I08 in Fig. '1, at which an inverter-operation firing-impulse is applied to the negative-group tube A2. at a point when the anode-voltage 109 of the tube is more positive than the cathode-voltage I [0, thus transferring the current from the tube A6 to the tube A2, in the commutating-time |08-H I.

This commutating action, with inverting operation of the negative-group tubes A6, A2 and A4, continues until the load-current becomes zero, as

indicated by the point 82 in Fig. 8, at which point the negative group of tubes A4, A8 and A2 ceases to carry inverter-current. The negative group of tubes thereafter ceases to carry current, until the next current-zero 84 (Fig. 8), when the rectifying action of this group of tubes recommences, as shown by the portion, H2, of the heavy-line voltage-curve in Fig. 6.

During the period 82-44 (Fig. 8) when the negative tube-group A4, A6, A2 is not carrying load-current, its respective tubes are still being fired, whenever their respective rectifier-firing peaks R4, R8, R2, or their inverter-firing peaks I4, I8, I2, become more positive than the critical gridvoltage 84, at a time when the anode-voltage of the tube is more positive than the cathode-voltage. Since the tubes of this negative group are not carrying current during this period 8284 in Fig, 6, the commutating-times become zero, resulting in substantially instantaneous transfer of the firingcondition from one tube to the next, as shown, for example, at I I8 in Fig. 6, which represents the first firing-time during the no-load operation 82-94 of the negative tube-group, when the inverterfiring peak I6, in Fig. '7, reaches the critical gridvoltage 84. During this entire no-load period 92-44, the negative tube-group A4, A6, A2 thus produces an output-voltage wave-portion, and it stands ready to deliver any current which may be demanded.

The operation of the positive group of tubes, AI A3 and A of Fig. 1, will be more or less apparent, from the foregoing description, upon reference to Figs. 4 and 5, remembering that the heavy line 8, in Fig. 4, represents substantially the cathodevoltage of the cathode-bus 8A, while the voltage-waves El, E8 and E5 represent the voltages which are impressed upon the respective anodes of the tubes of the positive group. No tube of the positive group will fire unless the instantaneous value of its output-voltage, as represented by the heavy line 8 in Fig. 4, is more negative than the instantaneous value of the impressed voltagewave El, E3 or E5, as the case may be, in Fig. 4.

Thus, let us consider the conditions when the first inverter-firing impulse occurs in Fig. 5, at the moment H4 whe the inverter-peak II hecomes suiiiciently positive to exceed the critical grid-voltage 84, so as to apply a firing-impulse to the tube AI of the positive-group, while the negative group of tubes is carrying a rectifying current 96 (Fig. 8). At this instant H4, when an inverter-firing impulse is applied to the tube Al, the cathode-voltage of the tube is practically the same as the impressed voltage-wave E2 on the previously inverting tube A5, as indicated by the point I IS on the heavy-line curve 8 in Fig. 4, while the anode-voltage of the tube AI is the value of the impressed voltage-wave EI-E4, at the moment, or the value I I6 (Fig. 4)

It will be notedthat the tube AI, at this inverter-firing moment H4, in Fig. 4, thus has an anode-voltage H6 which is more positive than the cathode-voltage H5, so that the tube AI fires during its inverter operation, producing an output-voltage and standing ready to deliver a loadcurrent in case the phase of the load-current 80, in Fig. 8, were such as to require positive current at this moment. Under the conditions which are assumed, for illustrative purposes, in the drawing, the load-current 98 (Fig. 8) is negative, at this moment H4, as shown at 86, and hence, except for a brief peak of circulating current, as subsequently described, the positive-voltage tube AI does not actually carry current, during the inverter-period of its operation, during the negative half, E4, of the voltage-wave EI which is impressed upon this tube.

Under the conditions shown in the drawing, the first load-carrying operation of the positive group of tubes occurs substantially at the moment when the load-current changes from a negative to a positive value, as shown by the point 92 in Fig. 8. At this instant, as shown in Fig. 4. the tube AI is receiving an excitation-current, which is supplied from the first or topmost ignitor-firing auxiliary tube 22 in Fig. 1. This excitation-current has been flowing in the tube AI since the moment H8 when the rectifying-firing impulse was applied to the corresponding auxiliary tube 22, as indicated by the moment H8 (Fig. 5) when the rectifying peak RI reaches the critical grid-voltage 84 in Fig. 5.

Consequently, at the current-zero 82, the tube AI begins carrying current as a rectifier, and supplies, to the output-circuit, the voltage H8 (Fig. 4) of the voltage-wave EI which is being applied to the tube AI at the moment. The operation thereafter continues as already explained,

Referring to Fig. 6, the angular distance, in input-frequency degrees, between the rectifyingflring point '91 and the preceding 3-phase voltage-crossing point 98 of Fig. 6 (assuming 3-phase rectifier-operation, as in Fig. 1), is called the delay-angle for the rectifier-peak R4, or the rectifying delay-angle. In like manner, the phase or time-delay, expressed in terms of input-frequency degrees, between the inverter-firing point I2I of the same tube and the same voltage-crossing point 88, is called the delay-angle for the inverter-peak I4, or the inverter delay-angle.

There is a phenomenon which is dependent upon the relation between the rectifier delayangle 98-8l, in Fig. 6, and the inverter advanceangle I 2II22, where I22 is the next voltagecrossing point, after the crossing-point 88. The inverter advance-angle I2I-I22 is equal, of course, to 180 minus the inverter delay-angle 98l2l. These two angles 88-81 and I2l-l22 are interdependent, because a peak of reactorcurrent flows, from one terminal 8A to the other terminal 8A, through the midtapped paralleling reactor I5A, from the rectifier tubes to the inverter tubes, at each of the voltage-crossing points, 98, I22, etc., for the successive phases.

Let us consider, for example, the voltage-differences which exist between the output-voltages 8 and 8 of the positive and negative tube-groups, just before and after the voltage-wave crossingpoint 88 in Figs. 4 and 6. At the point I I4 in Fig. 4, the positive-group voltage 8 changes from the value H5 to the value I I6, in Fig. 4, while the negative-group voltage 9 remains at the value I I5, as shown by Fig. 6, resulting in a positive half of a peak of circulating-current flowing from terminal 8A to terminal 8A through the paralleling reactor ISA in Fig. 1. At the voltagewave crossing-point 98, the two output-voltages 8 and 9 are equal, but a certain amount of flux is stored up in the paralleling reactor ISA.

If the rectifying delay-angle 9891 of the negative tube-group, in Fig. 6, is smaller than the inverting phase-lead I I4-88 of the positive tubegroup, in Fig. 4, the negative or flux-reducing portion of the circulating-current peak would not have a suflicient time-integrated value to demagnetize the iron 01 the paralleling reactor I 5A of Fig. 1, resulting in a certain progressive unidirectional increase in current in the paralleling reactor, at successive voltage-wave crossingpoints. There would thus be continuous circulating-current in the paralleling reactor, and the reactor-current peaks would reach a larger value than they would have, if the iron of the reactor had become demagnetized at each current-peak. These increased reactor-current peaks would be superimposed upon a direct-current component in the reactor. The harmonics and the power factor of the input-currents which are drawn from the input-circuit I would be deleteriously affected.

If the rectifying delay-angle 88-81 is made approximately equal to the inverter advanceangle II4-88, as approximately shown in Figs. 4 and 6, the circulating reactor-current, barring voltage-distortions in the theoretically sinusoidal wave E2 of the previously operating invertingtube A5, will have approximately equal positive and negative halves, so that there will be no progressive unidirectional increase in current in the paralleling reactor IA. This circulating reactorcurrent will then consist of a series of brief, disconnected, unidirectional peaks. The magnitude of these reactor-current peaks is a measure of the amounts of harmonics and lagging current which are drawn from the input-circuit I of the cycloconverter, even when the output-circuit of the converter is supplying a load-current at unity displacement-factor.

It is frequently desirable, as a factor of safety, or to provide for the contingency of a certain amount of distortion in the input-voltage waveform, to have the rectifying phase-lag 98-81 greater than the inverting phase-lead II4-98, as a safeguard to insure against a continuous direct-current component in the paralleling reactor I5A. A means is thus afforded, according to my present invention, whereby the input-wave form and power-factor may be somewhat improved, at the expense of a very slight reduction in the output-voltage, if desired.

The effective magnitude of the output-voltage with respect to the input-voltage may be varied, from a maximum to zero, by increasing the rectifying delay-angle 88-91 from the smallest reasonable value to approximately 80, or approximately the time represented by the horizontal distance 98-425 in Fig. 6, and simultaneously reducing the inverting delay-angle 88-I'2I, preferably in approximately the same amount, or from 88I2I to 88I25. If the rectifying and inverting phase-angles are changed in equal amounts in opposite directions, when either one is changed, the two phase-shifters 42 and 48 may be mechanically coupled together, with one of them connected in the opposite phase-sequence with respect to the other, as has been indicated in Fig. 1, wherein the two phase-shifters 42 and 48 are shown as being mounted on a common control-shaft I26.

The minimum practicable inverting advanceangle Il4--88 (Fig. 4), and hence the minimum practicable rectifying delay-angle 988I (Fig. 6), is of the order of 12 to 30 degrees. The limit is reached when the end of the inverting delayangle, such as 98-I2I (Fig. 6), approaches so closely to the voltage-crossing point I22 (Fig. 6) for that phase. that the end of the inverting In Fig. 6, and the next voltage-crossing point I21, to allow the inverting tube to become deionized. In other words, referring to the tube A8 which was inverting before the commutating operation, I08I'II, it is necessary for this commutating operation to be completed. so as to make said tube nonconducting, a certain finite time before the next voltage-crossing point I21 is reached, that is, before the anode-voltage, E2-E8, of the next-fired tube'A2, (which will also be the anodevoltage of the previously inverting tube A8). becomes positive with respect to the cathode-voltage, BIB-E8, of the previously inverting tube A8. The space within said previously firing tube A6 must first become deionized.

The duration of the inverter commutatingtime, such as I08-III of Fig. 6, is dependent upon the out-of-phase load-current at the moment, the voltage-diflerence between the circuits being commutated, and the commutating reactance of the supply-generator 2 of Fig. 1. If this reactance is low, a larger inverting delay-angle I08--III may be used with the same load-current, and still have a long enough deionizingcommutating-angle, such as is shown, for a different phase, at I08-I I I, will approach toward the next voltage-wave crossing-point I21, with an insufficient margin of safety.

It is necessary for a certain deionizing time to occur, between the point when the inverter-commutation has been completed, as indicated at III time before the reached.

As explained in the aforesaid copending joint application, the positive and negative groups of a pair of groups of tubes are not permitted to rectify at the same time. Referring to Fig. 6, the last negative-voltage tube to rectify, during the first rectification period of the negative group of tubes, is the tube A8, as shown by the portion I04, of the heavy-line curve in Fig. 6. This tube may remain rectifying from the firing-point I03 to the next voltage-zero 8|, provided that the load-current is sufficiently lagging, in power factor, to demand a negative current-wave until this voltage-zero point 8! is reached.

It should be noted that the rectification-period 88' of Fig. '7 could have ended at any time in relation to the input-frequency degrees, so that it could have ended at the rectifying firing-point I03 of this tube A8, which means that the rectification-blocking point 81 of Fig. 7 could have occurred at the time I03.

If the positive-group rectification-period 88 (Fig. 5) had been permitted to commence simultaneously with the discontinuance of the negative-group rectification-period 86' (Fig. '7), then the points 88 and 81 would both have coincided with each other, and, under the conditions just assumed, the points 88 and 81 would have coincided with the point I03, on the horizontal time-scale of Figs. 4 to '7. The first positive-group tube to be fired, for rectifying action, after the point I03, would then be the positivegroup tube AI. as shown by the RI firing-peak I28 in Fig. 5, and this action would occur 60 input-frequency degrees after the termination of the negative-group rectification-period at the point I03, which is the R6 firing-point. If the positive-voltage tube RI were permitted to fire at the RI firing-point I28, the resultant firingaction of the positive voltage tube AI would occur during a part of the period I03-8I (Fig. 6) during which the negative-voltage tube A8 would or could be firing, resulting in a large circulatory current, directly through the paralleling reactor I 8A, from the positive-voltage tube AI to the negative-voltage tube A8.

In order to prevent this simultaneous rectification-action, it is necessary to provide a timelag interval of at least 60 input-frequency degrees, between the termination 81 (or I03) of crossing-point I2] is the negative-group firing-period 86 in Fig. 7, and the initiation 88 of the positive-group rectification-period 86 in Fig. 5. With this minimum nonrectification interval of 60 input-cycle degrees, as covered by the previously mentioned copending joint application, the first positive-group tube which could fire, after the firing of the negativegroup tube A6, would be the positive-group tube A3, which would not fire until the point I29, which is after the voltage-zero 9| which terminates the longest possible rectifying-action of the negative-group tube A6.

While the immediately preceding discussion has had to do with 3-phase converter-operation, in which the successive voltage-waves are 120 apart, as shown in Figs. 6 and 8, the same principles would apply to 6-phase operation, with the understanding that the voltage-wave crossingpoint, with respect to which the rectifying and inverting delay-angles are measured, would be the crossing-point of six sinusoidal waves, spaced 60 apart, rather than three sinusoidal waves, spaced 120 apart.

When the output-circuit oi the cycloconverter is utilized to energize a motor III which is provided with a damper winding or short-circuited squirrel-cage secondary winding I3, as shown in Fig. 1, experience has shown that the motor is quite capable of performing satisfactorily on an output-wave-form having strong harmonics in it, either when the harmonics result from the blocked or square-topped form of the outputvoltage of the cycloconverter, in the output-circuit 4A, 4B, C of Fig. 1, or when the harmonics result from ripples which produce harmonics in the output-voltage wave. This is so, because the motor damping-winding I3 substantially blocks the harmonics from the wave-form of the flux of the motor, resulting in only a moderate increase in the heating of the motor because of the harmonics in the voltage which is supplied to the motor.

When the displacement-factor of the load on the output-circuit 4A, 4B, 40 of Fig. 1 is substantially unity, and can be maintained surely at unity, without risk of having any substantial wattless-current component, then it is not necessary for the inverter-controlling peakers to be used in our control-circuits, such as are shown at 40A-39A in Fig. 1, and these inverter-controlling peakers could then be either omitted entirely, or cut out of circuit during the unity-displacementfactor operation. As covered by a copending joint application of C. G. Hagensick and myself, Serial No. 739,723, filed April 5, 1947, the in clusion of these inverter-controlling peakers makes it possible to supply an output-circuit load which is not at unity displacement-factor, either during the motor-starting period, or under fault-conditions, or even during normal operating-conditions.

As covered by the first-mentioned joint application Serial No. 739,724, filed April 5, 1947, the illustrated control-circuit arrangement makes it readily possible to easily stop rectification in all of the cycloconverter-tubes 3, without removing the inverting firing impulses. This may readily be done by including a rectification-controlling switch I-3I in the single-pole modulator-frequency bias-reducing circuit, in Fig. 1, so as to make it impossible for the rotating commutator 30 to reduce the negative biasing-voltage to the point where the rectification peaks RI, R2, etc., can make the resultant grid-voltage attain the 16 critical firing-value 84. Thus, in Fig. 1, the rectiflcation-controlling switch I3I is connected in series between the positive battery-terminal 26 and the commutator slip-ring 36.

In accordance with my present invention, I sometimes utilize load-circuit capacitors I32, connected in parallel across the three-phase outputcircuit 4A, 4B, C, in Fig. 1. Parallel-connected load-circuit capacitors have been known before, in other converter-combinations, but they are particularly useful in combination or cooperation with the paralleling output-circuit reactors ISA, ISB and ISO. These reactors have to have a certain amount of input-frequency reactance, in order to limit the amount of fault-current which could flow, from terminal to terminal through the reactor, in the event of a fault on any one of the'cycloconverter-tubes. When such a tube-fault occurs, a heavy short-circuit or faultcurrent circulates through the reactor, from one group to the other group of pair of groups of cycloconverter-tubes, thus imposing a short-circuit on one or both of the alternating-current systems.

It is necessary \for the paralleling reactor ISA, etc., to have sufficient input-frequency reactance to limit this circulating short-circuit currentto a value which can be commutated by the tubes, so that the next good tube will clear the momentary fault which occurred in the faulted tube. The faulted tube may have time to recover, before it is called upon to carry current again, during its next operating-period in the cycle of operations.

A high reactance of the paralleling reactors ISA, ISB and ISC is undesirable, however, in the output-circuit 4A, 4B, 40, because it reduces the load-circuit displacement-factor and it also makes the voltage-regulation worse, that is, it makes the output-voltage droop more, as the load-current increases from zero to its maximum value. The amount of output-frequency reactance of each half of each of the paralleling reactors ISA, ISB and ISC can be reduced by reducing the ratio between the output-frequency and the input-frequency, that is, by applying the invention to applications having an output-frequency which is relatively low with respect to the input-frequency.

In this combination, the output-circuit capacitors I32 serve a doubly useful purpose, in not only correcting the adverse displacementfactor effect of the paralleling reactors ISA, ISB and ISC, in the output-circuit, but also filtering out some of the voltage-ripples from the output-circuit. The effect of the reactance of the paralleling reactors ISA, ISB and ISC, in series with the load, is to dampen out some of the ripples, and the effect of the Darallelconnected capacitors I3I is to also filter out the ripples, while counter-acting the bad displace merit-factor of the paralleling reactors. Thus the reactor-capacitor combination constitutes a means for controlling and improving the output wave-form.

An advantage of my paralleling reactors ISA, ISB and ISO is that they are independent of each other, so that the load-current harmonics do not reflect from one phase to another.

Fig. 2 shows a modification of the invention, in which twelve main tubes 3 can be used, instead of eighteen, as in Fig. 1. As compared with Fig. 1, tubes A5, A2, B3, B6, CI and C4, have been omitted. The load is still balanced on the input-circuit I. The several phases of the output-circuit 4A, 4B, =4C have voltages which are even more independent or each other than in Fig, 1. This is because the commutations oi! the load-current, from one tube to another, in Fig. 2, do not impose as great a change in wave-form, or the supply-circuit voltage, as in Fig. 1, and also because the input-frequency voltage-supply for each group of tubes is more independent, in Fig. 2, than in Fig. 1. Thus, the first two tube-groups; ALAS and A4, A6, of Fig. 2, are energized from the input-phases A and B, the second two tube-groups, Bl, B and B4, B2, are energized from the input-phases A and C, and thelast two tube-groups, C3, C5 and C6, C2, are energized from the input-phases B and C.

The independence of the voltages which are impressed upon the several phases of the main tubes 3, and hence the independence of the various phases oi. the voltages in the output-' circuits 4A, 4B, 40, may be increased by including anode or cathode reactors I40 in series with the main anode-cathode circuit of each of the cycloconverter-tubes 3, as shown in Fig. 2. This feature could also be incorporated in Fig. 1.

The reduction in the number or cycloconverter-tubes, in Fig. 2, besides making the different phase-voltages more independent of each other, results in a desirable reduction in the total number or items making up the complete equipment. This reduction in the number of the main tubes tends to increase the harmonics in the output-voltage waves, but this disadvantage can be at least partially offset by increasing the reactance oi. the paralleling reactors l-SA, I513 and ISO, and correspondingly increasing the ca pacity of the capacitors I32, so as to produce the desired wave-form, in a manner previously described.

While I have illustrated and explained my invention in its application to but a single basic general type of circuit-connection for the main anode-cathode circuits of the cycloconvertertubes, as shown in Figs. 1 and 2; and while I have illustrated and explained only a single preferred embodiment of control-circuits, as shown in Fig. 1, I wish it to be understood that my invention is not limited to the application, or to the specific control-circuit, which I have chosen for illustration, nor am I limited to my explanation of my present understanding of the theory and operation of my invention. I desire, therefore, that the appended claims shall be accorded the broadest construction consistent with their language.

I claim as my invention:

1. An electronic frequency-changer comprising one or more pairs of positive and negative groups of tubes, each tube having a controlcircuit, and having a main anode-and-cathode circuit; an alternating-current input-circuit associated with the tubes for interchanging inputfrequency energy with the tubes; an alternatingcurrent output-circuit conductor associated with a pair of groups for interchanging output- Irequency energy therewith; the positive .group of said pair of groups having a common cathodecircuit operating as an output-terminal for supplying the positive halves of the output-wave for said output-circuit conductor, the negative group of said pair of groups having a common anodecircuit operating as an output-terminal for supplying the negative halves of the output-wave for said output-circuit conductor; control-circuit excitation-means for exciting the control-circuits of the respective tubes, said control-circuit excitation-means including means for producing a control-voltage modulation at the outputfrequency; and a paralleling reactor for interconnecting said tube-group output-terminals and said output-circuit conductor, said paralleling reactor-comprising a midtapped winding having its terminals connected to the output-terminals of the positive and negative groups of said pair of groups, and having its midtap connected to said output-circuit conductor, the two halves of said mid-tapped winding being on a common magnetic circuit.

2. An electronic frequency-changer comprising a plurality of pairs of positive and negative groups of tubes, each tube having a control-circuit, and having a main anode-and-cathode circuit; an alternating-current input-circuit associated with the tubes for interchanging input-frequency energy with .the tubes; 2. polyphase altematingcurrent output-circuit associated with the several groups 0! tubes for interchanging outputfrequency energy therewith; each positive group of tubes having a common cathode-circuit operating as an output-terminal for supplying the positive halves of the output-wave for one of the output-circuit phases, each negative group of tubes having a common anode-circuit operating as an output-terminal for supplyi g the negative halves of the output-wave for the corresponding output-circuit phase; control-circuit excitationmeans for exciting the control-circuits of the respective tubes, said control-circuit excitationmeans including means for producing a controlvoltage modulation at the output-frequency; and a plurality of paralleling reactors for interconnecting said tube-group output-terminals and the respective output-circuit phases, each paralleling reactor comprising a midtapped winding having its terminals connected to the output-terminals or the positive and negative groups of one pair of groups of tubes, and having its midtap connected to the associated output-circuit phase, the two halves of each midtappecl winding being on a common magnetic circuit.

3. An electronic frequency-changer comprising one or more pairs of positive and negative groups of tubes, each tube having a control-circuit, and having a main anode-and-cathode circuit; an alternating-current input-circuit associated with the tubes for interchanging input-frequency energy with the tubes; an alternating-current output-circuit conductor associated with a pair of groups for interchanging output-frequency en- 'ergy therewith, the output-frequency being lower than the input-frequency; the positive group of said pair of groups having a common cathodecircuit operating as an output-terminal for supplying the positive halves of the output-wave for said output-circuit conductor, the negative group of said pair of groups having a common anodecircuit operating as an output-terminal for supplying the negative halves of the output-wave for said output-circuit conductor; control-circuit excitation-means for exciting the control-circuits of the respective tubes, said control circuit excitation-means including means for producing a control-voltage modulation at the input-frequency, and means for producing a control-voltage modulation at the output-frequency; and a paralleling reactor for interconnecting said tubegroup output-terminals and said output-circuit conductor, said paralleling reactor comprising a midtapped winding having its terminals connected to the output-terminals of the positive and negative groups of said pair of groups, and having its midtap connected to said output-circuit conduc- 19 tor, the two halves of said midtapped winding being on a common magnetic circuit.

4. An electronic frequency-changer comprising a plurality of pairs oi. positive and negative groups of tubes, each tube having a control-circuit, and having a main anode-and-cathode circuit: an alternating-current input-circuit associated with the tubes for interchanging input-frequency energy with the tubes; a polyph'ase alternating-current output-circuit associated with the several groups of tubes for interchanging output-trequency energy therewith, the output-frequency being lower than the input-frequency; each positive group oi tubes having a common cathodecircuit operating as an output-terminal i'or supplying the positive halves of the output-wave for one oi the output-circuit phases, each negative group of tubes having a common anode-circuit operating as an output-terminal for supplying the negative halves 01' the output-wave for the corresponding output-circuit phase; control-circuit excitation-means for exciting the controlcircuits of the respective tubes, said control-circuit excitation-means including means for producing a control-voitage modulation at the inputirequency, and means for producing a controlvoltage modulation at the output-frequency; and a plurality of paralleling reactors for interconnecting said tube-group output-terminals and the respective output-circuit phases, each paralleling reactor comprising a midtapped winding having its terminals connected to the output-terminals of the positive and negative groups of one pair 01' groups of tubes, and having its midtap con nected to the associated output-circuit phase, the two halves or each midtapped winding being on a common magnetic circuit.

5. The invention as defined in claim 1, characterized by said control-circuit excitation-means including input-frequency control-voltages so phased as to initiate both the rectifier-operation and the inverter-operation or each tube of the frequency-changer, provided that such initiation is not blocked by the output-frequency controlvoitage modulation, and provided that the tube has an anode-voltage which is more positive than its cathode-voltage at the moment, whereby each 20 group of tubes is, in general, capable of supplying a complete positive or negative hair of the outputvoltage wave, as the case may be, regardless oi the output-circuit power factor.

6. The invention as defined in c1aim 2, characterized by said control-circuit excitation-means including input-frequency control-voltages so phased as to initiate both the rectifier-operation and the inverter-operation of each tube of the frequency-changer, provided that such initiation is not blocked by the output-frequency controlvoltage modulation, and provided that the tube has an anode-voltage which is more positive than its cathode-voltage at the moment, whereby each group of tubes is, in general, capable of supplying a complete positive or negative halt oi. the outputvoltage wave, as the case may be, regardless of the output-circuit power factor.

7. The invention as defined in claim 3, characterized by said control-circuit excitation-means including input-frequency control-voltages so phased as to initiate both the rectifier-operation and the inverter-operation oi each tube'oi the frequency-changer, provided that such initiation is not blocked by the output-frequency controlvoltage modulation, and provided that the tube has an anode-voltage which is more positive than its cathode-voltage at the moment, whereby each group of tubes is, in general, capable of supplying a complete positive or negative half oi! the output-voltage wave, as the case may be, regardless of the output-circuit power factor.

8. The invention as defined in claim 4, characterized by said control-circuit excitation-means including input-frequency control-voltages so phased as to initiate both the rectifier-operation and the inverter-operation of each tube of the frequency-changer, provided that such initiation is not blocked by the output-frequency controlvoltage modulation, and provided that the tube has an anode-voltage which is more positive than its cathode-voltage at the moment, whereby each group oi tubes is, in general, capable of supplying a complete positive or negative half of the out put-voltage wave, as the case may be, regardless of the output-circuit power factor.

JOHN L. BOYER. 

